Technique for substantially eliminating temperature induced measurement errors from a coriolis meter

ABSTRACT

Apparatus and accompanying methods for inclusion in a Coriolis meter that substantially eliminate temperature induced measurement errors which might otherwise be produced by performance differences existing between the separate input channels contained in the meter. Specifically, two pairs of input channels are used in the meter. In operation, the meter repetitively measures the internal phase delay of each of these pairs and then subtracts the delay associated with each pair from actual flow based measurement data subsequently obtained therefrom. While one channel pair is measuring actual flow, the other channel pair is measuring its internal phase delay, with the channels being continuously cycled between these functions. Because both channel pairs are cycled at a sufficiently rapid rate, the current value of the internal phase delay for each of the pairs accurately reflects any temperature induced changes then occurring in the performance of that pair thereby eliminating substantially all temperature induced error components from the flow measurements subsequently obtained therefrom. In addition, the meter measures flow tube temperature in a manner that removes temperature induced errors therefrom.

CROSS REFERENCE TO RELATED APPLICATION

This application is a division of my copending patent application Ser.No. 07/728,546 filed on Jul. 11, 1991 and entitled "A TECHNIQUE FORSUBSTANTIALLY ELIMINATING TEMPERATURE INDUCED ERRORS FROM A CORIOLISMETER", U.S. Pat. No. 5,231,884.

CROSS-REFERENCE TO RELATED APPLICATION

This application describes and claims subject matter that is alsodescribed in a co-pending United States patent application entitled "ATECHNIQUE FOR DETERMINING A MECHANICAL ZERO VALUE FOR A CORIOLIS METER"from applicant R. Bruck, Ser. No. 728,547, filed simultaneously herewithand owned by the present assignee hereof now Pat. No. 5,228,327.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to apparatus and methods for inclusion in,illustratively, a Coriolis mass flow rate meter that substantiallyeliminate temperature induced measurement errors which might otherwisebe produced by performance differences existing between two separateinput channel circuits contained in the meter.

2. Description of the Prior Art

Currently, Coriolis meters are finding increasing use in a wide varietyof commercial applications as an accurate way to measure the mass flowrate of various process fluids.

Generally speaking, a Coriolis mass flow rate meter, such as thatdescribed in U.S. Pat. No. 4,491,025 (issued to J. E. Smith et al onJan. 1, 1985 and owned by the present assignee hereof--hereinafterreferred to as the '025 Smith patent), contains one or two parallelconduits, each typically being a U-shaped flow conduit or tube. Asstated in the '025 Smith patent, each flow conduit is driven tooscillate about an axis to create a rotational frame of reference. For aU-shaped flow conduit, this axis can be termed the bending axis. Asprocess fluid flows through each oscillating flow conduit, movement ofthe fluid produces reactionary Coriolis forces that are orthogonal toboth the velocity of the fluid and the angular velocity of the conduit.These reactionary Coriolis forces, though quite small when compared to aforce at which the conduits are driven, nevertheless cause each conduitto twist about a torsional axis that, for a U-shaped flow conduit, isnormal to its bending axis. The amount of twist imparted to each conduitis related to the mass flow rate of the process fluid flowingtherethrough. This twist is frequently measured using velocity signalsobtained from magnetic velocity sensors that are mounted to one or bothof the flow conduits in order to provide a complete velocity profile ofthe movement of each flow conduit with respect to either the otherconduit or a fixed reference. In dual conduit Coriolis meters, both flowconduits are oppositely driven such that each conduit oscillates(vibrates) as a separate tine of a tuning fork. This "tuning fork"operation advantageously cancels substantially all undesirablevibrations that might otherwise mask the Coriolis force.

In such a Coriolis meter, the mass flow rate of a fluid that movesthrough the meter is generally proportional to the time interval (theso-called "Δt" value) that elapses between the instant one pointsituated on a side leg of a flow conduit crosses a pre-determinedlocation, e.g. a respective mid-plane of oscillation, until the instanta corresponding point situated on the opposite side leg of the same flowconduit, crosses its corresponding location, e.g. its respectivemid-plane of oscillation. For parallel dual conduit Coriolis mass flowrate meters, this interval is generally equal to the phase differencebetween the velocity signals generated for both flow conduits at thefundamental (resonant) frequency at which these conduits are driven. Inaddition, the resonant frequency at which each flow conduit oscillatesdepends upon the total mass of that conduit, i.e. the mass of theconduit itself, when empty, plus the mass of any fluid flowingtherethrough. Inasmuch as the total mass varies as the density of thefluid flowing through the conduit varies, the resonant frequencylikewise varies with any changes in fluid density and, as such, can beused to track changes in fluid density.

For some time, the art has taught that both velocity signals areprocessed through at least some analog circuitry in an effort togenerate output signals that are proportional to the mass flow rate ofthe process fluid. In particular, the output signal associated with eachvelocity sensor is ordinarily applied through analog circuitry, e.g. anintegrator followed by a zero crossing detector (comparator), containedwithin a separate corresponding input channel. In this regard, seeillustratively U.S. Pat. Nos. 4,879,911 (issued to M. J. Zolock on Nov.14, 1989), 4,872,351 (issued to J. R. Ruesch on Oct. 10, 1989),4,843,890 (issued to A. L. Samson et al on Jul. 4, 1989) and 4,422,338(issued to J. E. Smith on Dec. 27, 1983)--all of which are also owned bythe present assignee hereof. While the various approaches taught inthese patents provide sufficiently accurate results in a wide array ofapplications, the meters disclosed in these references, as well assimilar Coriolis meters known in the art, nevertheless suffer from acommon drawback which complicates their use.

Specifically, Coriolis mass flow meters operate by detecting whatamounts to be a very small inter-channel phase difference between thesignals produced by both velocity sensors, i.e. the Δt value, andtransforming this difference into a signal proportional to mass flowrate. While, at its face, a Δt value is obtained through a timedifference measurement, this value, in actuality, is also a phasemeasurement. Using such a time difference measurement convenientlyprovides a way to accurately measure a manifestation of a phasedifference appearing between the velocity sensor signals. In Coriolismeters currently manufactured by the present assignee, this differencetends to amount to approximately 130 μsec at maximum flow. Each inputchannel in a Coriolis meter imparts some internal phase delay to itsinput signal. While the amount of this delay is generally quite small,it is often significant when compared to the small inter-channel phasedifference, i.e. 130 μsec or less, that is being detected. Currentlyavailable Coriolis meters have relied on assuming that each inputchannel imparts a finite and fixed amount of phase delay to itscorresponding velocity signal. As such, these Coriolis meters generallyrely on first measuring, at a true zero flow condition occurring duringmeter calibration, either the inter-channel phase difference (Δt) or theindicated mass flow rate. Subsequently, while metering actual flow,these meters will then subtract the resulting value, in some fashion,from either the measured Δt or mass flow rate value, as appropriate, inorder to generate an ostensibly accurate mass flow rate value for theprocess fluid then flowing therethrough.

Unfortunately, in practice, this assumption has proven to be inaccurate.First, not only does each input channel often produce a different amountof internal phase delay with respect to the other, but also the phasedelay that is produced by each channel is temperature dependent andvaries differently from one channel to the other with correspondingchanges in temperature. This temperature variability results in atemperature induced inter-channel phase difference. Because the measuredphase difference (Δt) that results from actual flow through the meter isrelatively small, then an error in the measured phase difference betweenthe velocity signals and attributable to the temperature inducedinter-channel phase difference can, in certain instances, besignificant. This error is generally not taken into account in currentlyavailable Coriolis mass flow rate meters. In certain situations, thiserror can impart a noticeable temperature dependent error into mass flowrate measurements, thereby corrupting the measurements somewhat.

In an effort to avoid this error, one well known solution in the art isto shroud an installed piped Coriolis meter, including its electronics,with a temperature controlled enclosure. This approach, which preventsthe meter from being exposed to external temperature variations andmaintains the meter at a relatively constant temperature while it is inoperation, greatly increases the installed cost of the meter and is thusnot suited for every application. Hence, in those applications whereinstalled cost is a concern, this approach is generally not taken.Specifically, in those applications and particularly where the meter isto be sited indoors and not exposed to wide temperature variations, thenthe measurement error which results from the temperature inducedinter-channel phase difference, while generally expected, tends toremain quite small and relatively constant. As such, this error isusually tolerated by a user. Unfortunately, in other applications wherethe meter is not housed in a temperature controlled enclosure, such asoutdoor installations where the meter is expected to experience widefluctuations in operating temperature, the error generally varies andcan become significant, and thus needs to be taken into account.

Apart from errors arising from temperature induced inter-channel phasedifferences, many currently available Coriolis mass flow rate metersalso disadvantageously exhibit an additional source of measurementinaccuracy related to temperature. In particular, Coriolis metersgenerally measure the temperature of the flow conduit and, owing tochanges in flow conduit elasticity with temperature, accordingly modifya meter factor value based upon the current temperature of the conduit.This meter factor, as modified, is then subsequently used toproportionally relate the inter-channel phase difference (Δt) value tomass flow rate. Flow conduit temperature is measured by digitizing anoutput of a suitable analog temperature sensor, such as a platinum RTD(resistive temperature device), that is mounted to an external surfaceof a flow conduit. The digitized output usually takes the form of afrequency signal, oftentimes produced by a voltage-to-frequency (V/F)converter, that is totalized (counted) over a given timing interval toyield an accumulated digital value that is proportional to flow conduittemperature. Unfortunately, in practice, V/F converters usually exhibitsome temperature drift which, based upon the magnitude of a change inambient temperature, could lead to an error, amounting to as much asseveral degrees, in the measurement of flow conduit temperature. Thiserror will, in turn, corrupt the mass flow rate.

A solution proposed in the art to ostensibly deal with temperaturedependent variations in the performance of the input channels ofCoriolis meters is taught in U.S. Pat. No. 4,817,448 (issued to J. W.Hargarten et al on Apr. 4, 1989 and also owned by the present assigneehereof--hereinafter referred to as the '448 Hargarten et al patent).This patent discloses a two channel switching input circuit for use in aCoriolis meter. In particular, this circuit includes a two-poletwo-throw FET (field effect transistor) switch located between theoutputs of the velocity sensors and the inputs to both of the channels.In one position, the FET switch connects the outputs of the left andright velocity sensors to corresponding inputs of the left and rightchannels, respectively; while in the opposite position, theseconnections are reversed. The switch is operated to change its positionat every successive cycle of flow conduit movement. In this manner, theoutput of each velocity sensor is alternately applied to both channelsin succession. Over a two cycle interval, appropriate time intervals aremeasured with respect to the velocity waveforms applied to both channelsand then averaged together to yield a single time interval value fromwhich errors attributable to each individual channel have been canceled.This resulting time interval value is then used in determining mass flowrate through the meter.

While this solution does indeed substantially eliminate temperatureinduced inter-channel phase differences, it possesses a drawback whichlimits its utility somewhat. Specifically, this input circuits in theapparatus taught in '448 Hargarten et al patent do not includeintegrators. Owing to the lack of any low pass filtering that would havebeen provided by integrators, these input circuits are thereforesusceptible to noise. Unfortunately, the switching scheme taught in thispatent does not permit integrators to be included in the switchedportion of the input circuitry, hence requiring that, to provide noiseimmunity, an integrator must be located after the FET switch.Unfortunately, in this location, the phase delay inherent in theintegrator can not be readily compensated, if at all. Inasmuch as theintegrator disadvantageously tends to provide the largest source ofphase delay in the input circuitry, inclusion of such an integratorwould add an error component, i.e. an uncompensated phase delay, to themeasured Δt values. Moreover, this phase delay would also vary withtemperature changes. Consequently, the resulting measured flow ratevalues would contain an error component. Thus, it became apparent thatthe solution posed in the '448 Hargarten et al patent has limitedapplicability to relatively noise-free environments.

Therefore, a need exists in the art for a Coriolis meter that providesaccurate flow and flow rate output values that are substantiallyinsensitive to ambient temperature variations and hence does notappreciably exhibit adverse temperature affects an could provideappreciable noise immunity. Such a meter should possess negligible, ifany, temperature induced measurement inaccuracies over relatively widevariations in ambient temperature thereby permitting the meter to beused to provide highly accurate flow measurements in a wide variety ofapplications and particularly without a need to house the meter in atemperature controlled enclosure. Advantageously, the increasedmeasurement accuracy provided by such a meter and the attendantinstalled cost savings associated therewith would likely broaden therange of applications over which such a meter could be used.

SUMMARY OF THE INVENTION

An object of the present invention is to provide a Coriolis meter thatprovides accurate output measurements that are substantially insensitiveto variations in ambient temperature.

A specific object is to provide such a meter that substantially, if nottotally, eliminates the need for a temperature controlled enclosure.

Another specific object is to provide a Coriolis meter in which themeasured flow and flow rate values do not contain appreciable error, ifany at all, that would otherwise result from switching transientsappearing in the input channels.

These and other objects are accomplished in accordance with theteachings of my invention by cycling the operation of each channel,particularly using a relatively short period, between: (a) measuring theinternal phase delay of that channel and (b) measuring raw flow based Δtvalue(s). The raw value(s) are then compensated, typically bysubtracting, the measured phase delay value therefrom in order to yielda corrected Δt value. A current value mass flow rate is then determinedusing the corrected rather than, as occurs in the art, the raw Δtvalue(s).

Specifically, the two identical input channels (i.e. left and right), ascommonly used in prior art Coriolis flow meters, are replaced with twopairs of input channels (i.e. pairs A-C and B-C) that permit the currentinternal phase delay exhibited by each channel pair to be measured. Eachof the channel pairs is operated to cycle between measuring its owninternal phase delay, i.e. a "zeroing" mode, and measuring Δt values foractual flow conditions, i.e. a "measurement" mode. Given the short cycletime, the current phase delay value accurately reflects any temperatureinduced changes then occurring in the performance of each channel pair.Once the current internal phase delay value is known for each pair, thatvalue is then used to correct flow based Δt values subsequently producedby that pair during its next measurement mode. Because the Δt flow basedmeasurements provided by each channel pair are corrected for the currentinternal phase delay associated with that particular pair, these Δtvalues do not contain any appreciable temperature induced errorcomponents regardless of the ambient temperature of the meter and itsvariation. As such, a Coriolis meter constructed in accordance with myinvention, can advantageously be used in environments with widelyvarying temperatures with essentially no diminution in accuracy owing totemperature changes.

In accordance with the teachings of a preferred embodiment of myinvention, my inventive flow measurement circuit utilizes three separatesimilar input channels (i.e. channels A, B and C) through whichinter-channel phase difference measurements are successively andalternately taken for each of two pairs, i.e. pairs A-C and B-C, of thethree channels. Channel C serves as a reference channel and iscontinuously supplied with one of the two velocity waveform sensorsignals, and specifically for purposes of the preferred embodiment theleft velocity sensor signal, as its input signal. The input to channelsA and B is either the left or right velocity sensor signals. While boththe zero and measurement modes involve measuring the inter-channel phasedifference in a pair of channels, the principal distinction between themodes is that in the zero mode, the same velocity sensor signal isapplied to both channels in that pair so that the resultinginter-channel phase difference measurement provides a measurement of theinternal phase delay for that pair; while, in the measurement mode, theleft and right velocity signals are applied to different correspondingchannels in that pair so as to provide a measurement, thoughuncorrected, of the current flow based Δt value for subsequent use indetermining current mass flow and flow rate values. Though inter-channelphase difference (Δt) measurements are taken during both modes, tosimplify matters and avoid confusion, I will distinguish between thesevalues in terms of their occurrence. I will henceforth refer to thosephase measurements which occur during the zero mode as beinginter-channel phase difference measurements and those which occur duringthe measurement mode as being Δt values.

Specifically, for any channel pair operating in the zero mode, such aspair A-C, the same, i.e. left, velocity sensor signal is applied to theinputs of both channels in that pair. Inter-channel phase differencemeasurements are then successively and repetitively taken during aso-called "zeroing" interval with the results being averaged during thisinterval. Ideally, if both of the channels in this pair exhibit the sameinternal phase delay, i.e. the phase delay through channel A equals thatof reference channel C, then the resulting inter-channel phasedifference measurements will all equal zero. However, in actuality, atany instant, all three channels usually possess different internal phasedelays. Nevertheless, since the phase delay for each pair is measuredwith respect to the same reference channel, i.e. channel C, anydifferences in the phase delay between the two pairs is caused bydifferences in the internal phase delay occurring between channels A andB. Once the "zeroing" interval has terminated, the input to thenon-reference channel in that pair is switched to the other velocitysensor signal, i.e. the right velocity sensor signal. A finite period oftime, i.e. including a so-called "switching" interval, is then allowedto expire before that channel pair is operated in the "measurement" modeduring which flow based Δt values are measured. The switching intervalis sufficiently long to enable all resulting switching transients tosettle out.

While one pair of channels, e.g. A-C, is operating in its zero mode, theother pair, e.g. B-C, is operating in its measurement mode in order toprovide continuous flow metering. For any channel pair, each successivecurrent flow based Δt value obtained during its measurement mode iscompensated by, typically subtracting, the most recent value of theinternal phase delay that has been measured for this channel pair duringits preceding zero mode.

The time during which one channel pair operates in the measurement mode,i.e. the measuring interval, equals the entire time that the other pairoperates in the zero mode. This latter time includes the time duringwhich the latter channel switches its non-reference channel input fromthe right to the left velocity sensor signal, then performs zeroing, andfinally switches its non-reference channel input from the left back tothe right velocity sensor signal.

At the conclusion of the measurement interval, the channel pairs simplyswitch modes, with illustratively channel pair B-C initially switchingits non-reference channel input from the right to the left velocitysensor signal, and channel pair A-C commencing flow based Δtmeasurements. Once this input switching is complete, channel pair B-Cthen undertakes zeroing followed by channel switching in the oppositedirection--while channel pair A-C remains in the measurement mode, andso on for successive cycles of operation.

Furthermore, in accordance with my inventive teachings, temperatureinduced errors in the temperature measurement of the flow conduitprovided through the RTD, and specifically associated with temperaturedrift in the V/F converter, are also advantageously eliminated.Specifically, to eliminate these errors, two reference voltages, inaddition to the RTD voltage, are selectively and successively convertedthrough the V/F converter into frequency values, in terms of counts, andare then used to define a linear relationship, specifically aproportionality factor, that relates the counted frequency value tomeasured flow conduit temperature. Then, by simply multiplying thecounted frequency value for the RTD voltage by this factor, a value forthe corresponding measured flow conduit temperature results. Inasmuch asthe reference voltages do not appreciably change, if at all, withtemperature variations and are each repetitively converted through theV/F converter at a relatively short periodicity, on the order ofillustratively 0.8 seconds, any temperature drift produced by the V/F isaccurately reflected in the resulting counted frequency values for thereference voltages themselves. Since temperature drift equally affectsthe counted values for both reference voltages and the RTD voltage, butdoes not change the relationships thereamong, the proportionality factorwhen multiplied by the counted frequency value for the RTD voltageproduces a true temperature value that is substantially independent ofany temperature drift produced by the V/F converter. By eliminatingtemperature induced errors in the measured temperature, the meter factorwill be appropriately modified in a manner that accurately reflectschanges in flow conduit temperature.

Furthermore, while my inventive meter determines a current mechanicalzero value (i.e. the zero flow offset value of the meter) based upon anumber of no flow Δt measurements taken during meter calibration, afeature of my inventive meter is to use that value in subsequentlycompensating actual flow measurements only if the noise content of theseno flow Δt measurements is sufficiently low, otherwise that value isignored. The number of no flow Δt measurements is governed by any ofthree factors: (a) whenever the standard deviation of these measurementsfalls below a convergence limit, (b) whenever a user manually terminatesthe mechanical zero process, or (c) if a pre-defined maximum number ofsuch measurements has been taken.

BRIEF DESCRIPTION OF THE DRAWINGS

The teachings of the present invention may be clearly understood byconsidering the following detailed description in conjunction with theaccompanying drawings, in which:

FIG. 1 is an overall diagram of Coriolis mass flow rate metering system5;

FIG. 2 depicts a high level block diagram of well known meterelectronics 20 shown in FIG. 1;

FIG. 3 shows the correct alignment of the drawing sheets for FIGS. 3Aand 3B;

FIGS. 3A and 3B collectively depict a high level block diagram of apreferred embodiment of flow measurement circuit 30 according to mypresent invention;

FIG. 4 shows the correct alignment of the drawing sheets for FIGS. 4Aand 4B;

FIGS. 4A and 4B collectively depict a timing diagram of the operationsperformed by channel pairs A-C and B-C in flow measurement circuit 30shown in FIGS. 3A and 3B;

FIG. 5 depicts a state table of circuit 70 that is contained within flowmeasurement circuit 30 shown in FIGS. 3A and 3B;

FIG. 6 depicts a simplified flowchart of Flow Measurement Basic MainLoop 600 that is executed by microprocessor 80 that is contained withinflow measurement circuit 30 shown in FIGS. 3A and 3B;

FIG. 7 shows the correct alignment of the drawing sheets for FIGS. 7Aand 7B;

FIGS. 7A and 7B collectively depict a flowchart of Zero DeterminationRoutine 700 that is executed as part of Main Loop 600 shown in FIGS. 6Aand 6B;

FIG. 8 shows the correct alignment of the drawing sheets for FIGS. 8Aand 8B;

FIGS. 8A and 8B collectively depict a flowchart of Mechanical ZeroRoutine 800 that is executed as part of Zero Determination Routine 700shown in FIGS. 7A and 7B;

FIG. 9 diagrammatically shows the zeroing operations that occur for eachcorresponding range in the standard deviation, i.e. σ.sub.Δt, of themeasured Δt values that are obtained during a mechanical zero process;

FIG. 10 diagrammatically shows the ranges of acceptable andnon-acceptable mechanical zero values; and

FIG. 11 shows a flowchart of RTD Temperature Processing Routine 1100which is executed on a periodic interrupt basis by microprocessor 80that is contained within inventive flow measurement circuit 30 shown inFIGS. 3A and 3B.

To facilitate understanding, identical reference numerals have beenused, where appropriate, to designate identical elements that are commonto the figures.

DETAILED DESCRIPTION

After reading the following description, those skilled in the art willreadily appreciate that my inventive technique can be incorporatedwithin a wide variety of circuitry that measures multiple inputs usingmultiple analog input channels. Advantageously, use of my inventionsubstantially, if not totally, eliminates errors that might otherwisearise from performance differences occurring among the individualchannels and attributable to, for example, temperature, aging and/orother phenomena that differently affect the analog circuitry containedtherein. Of course, such usage would include any Coriolis meterregardless of whether that meter is measuring flow, flow rate, densityor other parameter(s) of a process fluid. Nevertheless, for purposes ofbrevity, my inventive input circuit will be discussed in the context ofa dual conduit (tube) Coriolis meter that specifically measures massflow rate and totalized mass flow.

FIG. 1 shows an overall diagram of Coriolis mass flow metering system 5.

As shown, system 5 consists of two basic components: Coriolis meterassembly 10 and meter electronics 20. Meter assembly 10 measures themass flow rate of a desired process fluid. Meter electronics 20,connected to meter assembly 10 via leads 100, illustratively providesmass flow rate and totalized mass flow information. Mass flow rateinformation is provided over leads 26 in frequency form and in scaledpulse form. In addition, mass flow rate information is also provided inanalog 4-20 mA form over leads 26 for easy connection to downstreamprocess control and/or measurement equipment.

Coriolis meter assembly 10, as shown, includes a pair of manifolds 110and 110'; tubular member 150; a pair of parallel flow conduits (tubes)130 and 130'; drive mechanism 180; a pair of velocity sensing coils160_(L) and 160_(R) ; and a pair of permanent magnets 170_(L) and170_(R). Conduits 130 and 130' are substantially U-shaped and have theirends attached to conduit mounting blocks 120 and 120', which are, inturn, secured to respective manifolds 110 and 110'. Both flow conduitsare free of pressure sensitive joints.

With the side legs of conduits 130 and 130' fixedly attached to conduitmounting blocks 120 and 120' and these blocks, in turn, fixedly attachedto manifolds 110 and 110', as shown in FIG. 1, a continuous closed fluidpath is provided through Coriolis meter assembly 10. Specifically, whenmeter 10 is connected, via inlet end 101 and outlet end 101', into aconduit system (not shown) which carries the process fluid that is beingmeasured, fluid enters the meter through an orifice in inlet end 101 ofmanifold 110 and is conducted through a passageway therein having agradually changing cross-section to conduit mounting block 120. There,the fluid is divided and routed through flow conduits 130 and 130'. Uponexiting flow conduits 130 and 130', the process fluid is recombined in asingle stream within conduit mounting block 120' and is thereafterrouted to manifold 110'. Within manifold 110', the fluid flows through apassageway having a similar gradually changing cross-section to that ofmanifold 110--as shown by dotted lines 105--to an orifice in outlet end101'. At end 101', the fluid reenters the conduit system. Tubular member150 does not conduct any fluid. Instead, this member serves to axiallyalign manifolds 110 and 110' and maintain the spacing therebetween by apre-determined amount so that these manifolds will readily receivemounting blocks 120 and 120' and flow conduits 130 and 130'.

U-shaped flow conduits 130 and 130' are selected and appropriatelymounted to the conduit mounting blocks so as to have substantially thesame moments of inertia and spring constants about bending axes W--W andW'--W', respectively. These bending axes are perpendicularly oriented tothe side legs of the U-shaped flow conduits and are located nearrespective conduit mounting blocks 120 and 120'. The U-shaped flowconduits extend outwardly from the mounting blocks in an essentiallyparallel fashion and have substantially equal moments of inertia andequal spring constants about their respective bending axes. Inasmuch asthe spring constant of the conduits changes with temperature, resistivetemperature detector (RTD) 190 (typically a platinum RTD device) ismounted to one of the flow conduits, here conduit 130', to continuouslymeasure the temperature of the conduit. The temperature of the conduitand hence the voltage appearing across the RTD, for a given currentpassing therethrough, will be governed by the temperature of the fluidpassing through the flow conduit. The temperature dependent voltageappearing across the RTD is used, in a well known method, by meterelectronics 20 to appropriately compensate the value of the springconstant for any changes in conduit temperature. The RTD is connected tometer electronics 20 by lead 195.

Both of these flow conduits are driven, typically sinusoidally, inopposite directions about their respective bending axes and atessentially their common resonant frequency. In this manner, both flowconduits will vibrate in the same manner as do the tines of a tuningfork. Drive mechanism 180 supplies the oscillatory driving forces toconduits 130 and 130'. This drive mechanism can consist of any one ofmany well known arrangements, such as a magnet mounted to illustrativelyflow conduit 130' and an opposing coil mounted to illustratively flowconduit 130 and through which an alternating current is passed, forsinusoidally vibrating both flow conduits at a common frequency. Asuitable drive signal is applied by meter electronics 20, via lead 185,to drive mechanism 180.

With fluid flowing through both conduits while these conduits are drivenin opposing directions, Coriolis forces will be generated along adjacentside legs of each of flow conduits 130 and 130' but in oppositedirections, i.e. the Coriolis force generated in side leg 131 willoppose that generated in side leg 131'. This phenomenon occurs becausealthough the fluid flows through the flow conduits in essentially thesame parallel direction, the angular velocity vectors for theoscillating (vibrating) flow conduits are situated in opposite thoughessentially parallel directions. Accordingly and as a result of theCoriolis forces, during one-half of the oscillation cycle of both flowconduits, side legs 131 and 131' will be twisted closer together thanthe minimum distance occurring between these legs produced by just theoscillatory movement of the conduits generated by drive mechanism 180.During the next half-cycle, the generated Coriolis forces will twistside legs 131 and 131' further apart than the maximum distance occurringbetween these legs produced by just the oscillatory movement of theconduits generated by drive mechanism 180.

During oscillation of the flow conduits, the adjacent side legs, whichare forced closer together than their counterpart side legs, will reachthe end point of their travel, where their velocity crosses zero, beforetheir counterparts do. The time interval (also referred to herein as theinter-channel phase difference, or time difference or simply Δ"t" value)which elapses from the instant one pair of adjacent side legs reachestheir end point of travel to the instant the counterpart pair of sidelegs, i.e. those forced further apart, reach their respective end pointis substantially proportional to the mass flow rate of the fluid flowingthrough meter assembly 10. The reader is referred to U.S. Pat. No.4,491,025 (issued to J. E. Smith et al on Jan. 1, 1985) for a moredetailed discussion of the principles of operation of parallel pathCoriolis flow meters than that just presented.

To measure the time interval, Δt, coils 160_(L) and 160_(R) are attachedto either one of conduits 130 and 130' near their free ends andpermanent magnets 170_(L) and 170_(R) are also attached near the freeends of the other one of the conduits. Magnets 170_(L) and 170_(R) aredisposed so as to have coils 160_(L) and 160_(R) located in the volumeof space that surrounds the respective permanent magnets and in whichthe magnetic flux fields are essentially uniform. With thisconfiguration, the electrical signal outputs generated by coils 160_(L)and 160_(R) provide a velocity profile of the complete travel of theconduits and can be processed, through any one of a number of well knownmethods, to determine the time interval and, in turn, the mass flow rateof the fluid passing through the meter. In particular, coils 160_(L) and160_(R) produce the left and right velocity signals that appear on leads165_(L) and 165_(R), respectively. As such, coils 160_(L) and 160_(R)and corresponding magnets 170_(L) and 170_(R) respectively form the leftand right velocity sensors. While at its face Δt is obtained through atime difference measurement, Δt is in actuality a phase measurement.Using a time difference measurement here provides an accurate way tomeasure a manifestation of the phase difference that occurs between theleft and right velocity sensor signals.

As noted, meter electronics 20 accepts as input the RTD signal appearingon lead 195, and the left and right velocity signals appearing on leads165_(L) and 165_(R), respectively. Meter electronics 20 also produces,as noted, the drive signal appearing on lead 185. Leads 165_(L),165_(R), 185 and 195 are collectively referred to as leads 100. Themeter electronics processes both the left and right velocity signals andthe RTD signal to determine the mass flow rate and totalized mass flowof the fluid passing through meter assembly 10. This mass flow rate isprovided by meter electronics 20 on associated lines within leads 26 inanalog 4-20 mA form. Mass flow rate information is also provided infrequency form (typically with a maximum range of 0-10 KHz) over anappropriate line within leads 26 for connection to downstream equipment.

A block diagram of meter electronics 20, as known in the art, isdepicted in FIG. 2. Here, as shown, meter electronics 20 consists offlow measurement circuit 23, flow tube drive circuit 27 and display 29.

Flow tube drive circuit 27, depicted in FIG. 2, provides an appropriaterepetitive alternating or pulsed drive signal, via lead 185, to drivemechanism 180. This circuit synchronizes the drive signal to the leftvelocity signal which appears on leads 165_(L) and 25. In operation,circuit 27 maintains both flow tubes in opposing sinusoidal vibratorymotion at a fundamental resonant frequency. As is known in the art, thisfrequency is governed by a number of factors, including variouscharacteristics of the tubes themselves and the density of the processfluid flowing therethrough. Since circuit 27 is very well known in theart and its specific implementation does not form any part of thepresent invention, this circuit will not be discussed in any furtherdetail herein. In this regard, the reader is illustratively referred toU.S. Pat. Nos. 5,009,109 (issued to P. Kalotay et al on Apr. 23, 1991);4,934,196 (issued to P. Romano on Jun. 19, 1990) and 4,876,879 (issuedto J. Ruesch on Oct. 31, 1989)--all of which are owned by the presentassignee hereof and describe different embodiments for the flow tubedrive circuit.

Flow measurement circuit 23 processes the left and right velocitysignals appearing over leads 165_(L) and 165_(R), respectively, alongwith the RTD signal appearing on lead 195, in a well known manner, todetermine the mass flow rate and totalized mass flow of the processfluid passing through meter assembly 10. The resulting mass flow rateinformation is provided as a 4-20 mA output signal over lead 263, foreasy connection to additional downstream process control equipment (notshown), and as a scaled frequency signal over lead 262 for easyconnection to a remote totalizer (also not shown). The signals appearingon leads 262 and 263 form part of the process signals that collectivelyappear on leads 26 shown in FIG. 1. Other leads (not specifically shown)within leads 26 provide totalized flow information, as well as otherprocess parameters, in digital form for connection to suitable display,telemetry and/or downstream processing equipment.

Inasmuch as the method through which flow measurement circuit 23generates mass flow and totalized flow rate information is well known tothose skilled in the art, only that portion of its constituentelectronics that are germane to the present invention will be discussedhereinafter. In this regard, measurement circuit 23 contains twoseparate input channels: left channel 202 and right channel 212. Eachchannel contains an integrator and two zero crossing detectors. Withinboth channels, the left and right velocity signals are applied torespective integrators 206 and 216, each of which effectively forms alow pass filter. The resulting outputs of these integrators are appliedto zero crossing detectors (effectively comparators) 208 and 218, eachof which generates a level changes whenever the corresponding integratedvelocity signal exceeds a voltage window defined by a small predefinedpositive and negative voltage level, e.g. ±v. The outputs of both zerocrossing detectors 208 and 218 are fed as control signals to counter 220in order to measure a timing interval, in terms of clock pulse counts,that occurs between corresponding changes in these outputs. Thisinterval is the well known Δt value and varies with the mass flow rateof the process fluid. The resulting Δt value, in counts, is applied, inparallel, as input data to processing circuitry 235. In addition, RTD190 is connected to an input of RTD input circuit 224 which supplies aconstant drive current to the RTD, linearizes the voltage that appearsacross the RTD and converts this voltage using voltage/frequency (V/F)converter 226 into a stream of pulses that has a scaled frequency whichvaries proportionally with any changes in RTD voltage. The resultingpulse stream produced by circuit 224 is applied as an input to counter228 which periodically counts the stream and produces a value, incounts, that is proportional to the measured temperature. The contentsof counter 228 are also applied in parallel as input data to processingcircuit 235. Processing circuit 235, which is typically a microprocessorbased system, determines the current mass flow rate from the digitizedΔt and temperature values applied thereto. In this regard, the digitizedtemperature value is used to modify a meter factor value based upon thecurrent temperature of the flow tubes and, by doing so, account forchanges in flow tube elasticity with temperature. The meter factor, asmodified, (i.e. a temperature compensated meter factor--RF) is thensubsequently used to proportionally determine the mass flow rate fromthe current measured Δt value. Having determined the mass flow rate,circuitry 235 then updates totalized mass flow and also provides, forexample, suitable mass flow rate output signals over leads 26 forconnection to local display 29 and/or to downstream process controlequipment.

It is now become apparent that the analog circuitry contained within theleft and right channels disadvantageously injects some error into theresulting mass flow and mass flow rate values produced by processingcircuitry 235. Specifically, not only does each input channel oftenpossess a different amount of internal phase delay with respect to theother, as measured from the input of an integrator to an output of itszero crossing detectors, but also the phase delay that is internallyproduced by each channel is temperature dependent and often variesdifferently from one channel to the other with corresponding changes intemperature. As such, left channel 202 may, for example, exhibit phasedelay that has a different temperature dependent variation than thatexhibited by right channel 212. This variability results in atemperature induced inter-channel phase difference that manifests itselfas an error component in the measured Δt value. Because the Δt valuethat results from actual flow itself through the meter is relativelysmall, this error component can, in certain instances, be significant.This error is generally not taken into account in currently availableCoriolis mass flow rate meters. In certain situations, particularlywhere the meter is situated in an outdoors environment and subjected towide temperature fluctuations, this error can impart a noticeabletemperature dependent error into mass flow rate measurements, therebycorrupting these measurements somewhat.

Now, apart from temperature dependent errors in the measured Δt value,the temperature measurement circuitry itself imparts an additionalsource of temperature induced measurement error into the mass flow andflow rate values produced by processing circuitry 235. In this regard,V/F converter 226 contained within RTD input circuit 224 exhibits, as donearly all such converters, measurable temperature drift. This drift,based upon the magnitude of a change in ambient temperature, may lead toan error, amounting to as much as several degrees, in the measurement ofthe flow conduit temperature. This error will, in turn, lead to errorsin the modified meter factor which, in turn, will also corrupt the massflow rate and totalized mass flow values.

To eliminate the deficiencies associated with Coriolis meters known inthe art and particularly those containing circuitry typified by flowmeasurement circuit 23, I have developed a technique for use in the flowmeasurement circuit of a Coriolis meter that advantageously renders themass flow and mass flow rate values produced by the meter substantiallyinsensitive to temperature changes thereby improving their overallaccuracy.

Specifically, in accordance with the teachings of my present invention,the two identical input channels (i.e. left and right), as commonly usedin prior art flow measurement circuits, are replaced with two pairs ofinput channels (i.e. pairs A-C and B-C) that permit the phase delayexhibited by each channel pair to be measured. Once the current value ofthe phase delay is known for each channel pair, that value issubsequently used to correct flow based Δt values subsequently measuredby that channel pair. Since each of the channel pairs is operated tocycle, on a relatively short period, between measuring its own internalphase delay, i.e. a "zeroing" mode, and measuring Δt values for actualflow conditions, i.e. a "measurement" mode, the current phase delayvalue accurately reflects any temperature induced changes then occurringin the performance of each channel pair. Because the Δt flow basedmeasurements provided by each channel pair are corrected for the currentinternal phase delay associated with that particular pair, these Δtvalues do not contain any appreciable temperature induced errorcomponents regardless of the ambient temperature of the meter and itsvariation. As such, a Coriolis meter constructed in accordance with myinvention, can advantageously be used in environments with widelyvarying temperatures with essentially no diminution in accuracy owing totemperature changes.

In particular, my inventive flow measurement circuit utilizes threeseparate similar input channels (i.e. channels A, B and C) through whichinter-channel phase difference measurements are successively andalternately taken for each of two pairs, i.e. pairs A-C and B-C, of thethree channels. Channel pair A-C contains channels A and C; whilechannel pair B-C contains channels B and C. Channel C serves as areference channel and is continuously supplied with one of the twovelocity waveform sensor signals, and specifically for purposes of thepreferred embodiment the left velocity sensor signal, as its inputsignal. The input to channels A and B is either the left or rightvelocity sensor signals. While both the zero and measurement modesinvolve measuring the inter-channel phase difference in a pair ofchannels, the principal distinction between the modes is that in thezero mode, the same, i.e. left, velocity sensor signal is applied toboth channels in that pair so that the resulting inter-channel phasedifference measurement provides a measurement of the internal phasedelay for that pair; while, in the measurement mode, the left and rightvelocity signals are applied to different corresponding channels in thatpair so as to provide a measurement, though uncorrected, of the currentflow based Δt value for subsequent use in determining current mass flowand flow rate values. Though inter-channel phase difference (Δt)measurements are taken during both modes, to simplify matters and avoidconfusion, I will distinguish between these values in terms of theiroccurrence. Thus, I will henceforth refer to those phase measurementswhich occur during the zero mode as being inter-channel phase differencemeasurements and those which occur during the zero mode as being Δtvalues. Also, both the inter-channel phase difference measurements andthe Δt values for any channel pair will be collectively and hereinafterreferred to as timing measurements.

Specifically, for any channel pair operating in the zero mode, such aspair A-C, the same, i.e. left, velocity sensor signal is applied to theinputs of both channels in that pair. Inter-channel phase differencemeasurements are then successively and repetitively taken during aso-called "zeroing" interval with the results being averaged during thisinterval. Ideally, if both of the channels in this pair exhibit the sameinternal phase delay, i.e. the phase delay through channel A equals thatof reference channel C, then the resulting inter-channel phasedifference measurements will all equal zero. However, in actuality, atany instant, all three channels usually possess different internal phasedelays. Nevertheless, since the phase delay for each pair is measuredwith respect to the same reference channel, i.e. channel C, anydifferences in the phase delay between the two pairs is caused bydifferences in the internal phase delay occurring between channels A andB. Once the "zeroing" interval has terminated, the input to thenon-reference channel in that pair is switched to the other velocitysensor signal, i.e. the right velocity sensor signal. A finite period oftime, i.e. including a so-called "switching" interval, is then allowedto expire before that channel pair is operated in the "measurement" modeduring which flow based Δt values are measured. The switching intervalis sufficiently long to enable all resulting switching transients tosettle out, e.g. for their amplitude to decay below a pre-defined level.

While one pair of channels, e.g. A-C, is operating in its zero mode, theother pair, e.g. B-C, is operating in its measurement mode. For anychannel pair, each successive measured flow based Δt value that isobtained during its measurement mode is compensated by, typicallysubtracting, the most recent value of the internal phase delay that hasbeen measured for this channel pair during its preceding zero mode.

The time during which one channel pair operates in the measurement mode,i.e. the measuring interval, equals the entire time that the other pairoperates in the zero mode. This latter time (i.e. the "zero" interval)includes the time (i.e. the "switching" interval) during which thelatter channel switches its non-reference channel input from the rightto the left velocity sensor signal, then performs zeroing (during aso-called "zeroing" interval), and finally switches its non-referencechannel input from the left back to the right velocity sensor signal.Note that the zero interval includes both two switching intervals and azeroing interval.

At the conclusion of the measurement interval, the channel pairs simplyswitch modes, with illustratively channel pair B-C initially switchingits non-reference channel input from the right to the left velocitysensor signal, and channel pair A-C commencing flow based Δtmeasurements. Once this input switching is complete, channel pair B-Cthen undertakes zeroing followed by channel switching in the oppositedirection--while channel pair A-C remains in the measurement mode, andso on for successive cycles of operation. After a channel pair hascompleted the latter switching operation but before commencing itsoperation in the measurement mode, that channel can, if desired,undertake measurements of flow based Δt values for a finite period oftime, hereinafter referred to as the "active" interval, which, tosimplify implementation, has a duration equal to the "zeroing" interval.Since both channels can simultaneously provide flow based Δt valuesduring the "active" interval from both velocity sensor signals, then,ideally, in the absence of any noise, isolated perturbations ordifferences between the internal phase delays associated with the pairsof channels, the same Δt values should be produced by both channels.Hence, as an added check, one or more of the measured flow based Δtvalues obtained from each channel pair during the "active" interval canbe compensated by the most recent value of the measured phase delay forthat pair to yield corresponding pairs of corrected Δt values. The twovalues in each such pair could then be compared against each other. Asufficient discrepancy between the values in any of these pairs wouldgenerally signify an error condition.

Inasmuch as channel switching only occurs on the channel pair oppositefrom that which is being used to provide flow based measurements, anyswitching transients (and noise associated therewith) are effectivelyisolated from and advantageously do not corrupt the flow and flow ratemeasurements. Moreover, by allowing an appropriately long switchinginterval to expire even before zeroing begins, the switching transientsadvantageously do not affect the internal phase delay measurements forthe channel pair being zeroed. As such, the performance of a Coriolismeter that utilizes my invention is substantially, if not totally,immune from input switching transients and the like.

The specific length of time of the switching and zeroing intervals isnot critical. However, since switching transients die out rather quicklyand additional averaging generally provides increased accuracy for theinternal phase delay measurements, the switching interval is typicallyset to be much shorter than the zeroing interval. In this regard, theswitching interval, as measured in tube cycles, may last forillustratively 16-32 such cycles, while the zeroing interval may be setto consume upwards of illustratively 2048 such cycles.

Furthermore, in accordance with my inventive teachings, temperatureinduced errors in the temperature measurement of the flow tube providedthrough the RTD, and specifically associated with temperature drift inthe V/F converter, are also advantageously eliminated. Specifically, toeliminate these errors, two reference voltages in addition to the RTDvoltage are selectively and successively converted through the V/Fconverter into frequency values, in terms of counts, and are then usedto define a linear relationship, specifically a proportionality factor,that relates the counted frequency value to measured flow tubetemperature. Then, by simply multiplying the counted frequency value forthe RTD voltage by this factor, a value for the corresponding measuredflow tube temperature results. Inasmuch as the reference voltages do notappreciably change, if at all, with temperature variations and are eachrepetitively converted through the V/F converter at a relatively shortperiodicity, on the order of illustratively 0.8 seconds, any temperaturedrift produced by the V/F is accurately reflected in the resultingcounted frequency values for the reference voltages themselves. Sincetemperature drift equally affects the counted values for both referencevoltages and the RTD voltage, but does not change the relationshipsthereamong, the proportionality factor when multiplied by the countedfrequency value for the RTD voltage produces a true temperature valuethat is substantially independent of any temperature drift produced bythe V/F converter. By eliminating temperature induced errors in themeasured temperature, the meter factor will be appropriately modified ina manner that accurately reflects changes in flow tube temperature.

A. HARDWARE DESCRIPTION

With this description in mind, a high level block diagram of a preferredembodiment of inventive flow measurement circuit 30 is collectivelydepicted in FIGS. 3A and 3B, for which the correct alignment of thedrawing sheets for these figures is shown in FIG. 3.

In essence, flow measurement circuit 30 contains an input multiplexorand three similar input channels--one of which is reference channel C, afinite state machine with associated timing counters, and amicrocomputer system. The inputs to the two non-reference channels A andB are selected, through the multiplexor, by the finite state machine, asit cycles through its various states. The outputs from the threechannels are applied to the counters in order to generate the timingmeasurements, i.e. the inter-channel phase difference measurements andthe Δt values, for each of the two channel pairs A-C and B--C. Thetiming measurements provided by these counters along with the stateinformation from the finite state machine are supplied to themicrocomputer which, in turn, determines current corresponding values ofmass flow rate. In addition, the RTD output and two reference voltagesare sequentially converted into corresponding frequency values, throughan appropriate input switch, V/F converter and associated circuitry, andcounted through a timing counter associated with the finite statemachine. The resulting counts therefor are then supplied by this counterto the microcomputer for its use in properly modifying the meter factor.

Specifically, as depicted, flow measurement circuit 30 contains threesimilar input channels 44, 54 and 64, also respectively referred toherein as Channels A, C and B. in addition, this flow measurementcircuit also contains multiplexor 31, circuit 70, analog switch 35,reference voltage generator 39, RTD input circuit 42, microcomputer 80,output circuitry 90 and input circuitry 95.

RTD input circuit 42, shown in FIGS. 3A and 3B, performs the samefunctions and contains essentially the same circuitry as RTD inputcircuit 224 shown in FIGS. 2A and 2B and discussed above.

Each of channels A and B, of which channel A is illustrative, containsinput analog circuitry, which is simply represented as an amplifierconnected to a level detector. With respect to channel A, amplifier 46provides appropriate input filtering of the left velocity sensor signal,level shifting and amplification of the resulting shifted signal. Leveldetectors 48, effectively a windowing comparator, provides a levelchange on its output signal whenever the output signal produced byamplifier 46 increases above or decreases below a small fixed positiveand negative voltage. In this regard, each of these channels providesessentially the same functions as corresponding circuitry in flowmeasurement circuit 23 shown in FIG. 2. Channel C shown in FIGS. 3A and3B contains circuitry represented by amplifier 56 and level detector 58.Reference channel C is quite similar to channels A and B with theexception that level detector 58 contains a single level detector,rather than a windowing comparator, to detect whenever the output signalfrom amplifier 56 exceeds a small positive voltage level. Multiplexor31, which is illustratively formed of three separate 2-to-1 multiplexorsselectively routes either the left velocity sensor signal appearing onlead 165_(L) or the right velocity sensor signal appearing on lead165_(R) to the input of each of the three channels. In this regard, theleft and right velocity sensor signals are applied to the first (A₀, B₀and C₀) and second (A₁, B₁ and B₁) inputs, respectively, of multiplexor31. The status of select signals S₀, S₁ and S₂ specifies whether theright or left velocity sensor signal is applied to the three separate(O_(A), O_(B), and O_(C)) outputs of the multiplexor. Select signals 33,formed of signals RPO₋₋ A and RPO₋₋ B connected to select inputs S₀ andS₁, cause the multiplexor to separately route either the left or rightvelocity sensor signals as the inputs to channels A and B, respectively;while grounded select signal S₂ causes multiplexor 31 to continuouslyroute the left velocity sensor signal appearing on lead 165_(L) to theinput of reference channel C. Select signals 33 are set by control logic72 in circuit 70 to perform appropriate input switching.

Circuit 70 contains control logic 72 and timing counters 74, 76 and 78.Circuit 70, preferably formed of a single application specificintegrated circuit, is essentially a finite state machine that defines aperiodic and repetitively occurring sequence of timing intervals andaccompanying states. During each such timing interval, externallyapplied input signals can start and stop an appropriate timing counter.At the conclusion of that interval, the contents of that timing countercan be read in parallel form for subsequent use. As this circuit appliesto flow measurement circuit 30, timing counters 74 and 76, groupedtogether as counters 75, are used to determine the timing measurementsfor channel pairs A-C and B-C, respectively. Timing counter 78 is usedto count the frequency value produced by RTD input circuit 42 for aselected analog input signal applied thereto through switch 35. Thiscounter is reset by control logic 72 prior to each conversion intervalby applying an appropriate signal being applied to lead 79. Controllogic 72 is formed of well known combinatorial and other logic. Afterhaving been initialized with the duration, in tube cycles, of thezeroing and switching intervals, the control logic generates selectsignals over leads 33 to operate multiplexor 31 to select and route theproper waveform sensor signals to the inputs of either channel A or B,as appropriate, such that the channel pairs are repetitively andoppositely cycled through their zero and measurement modes. In addition,control logic 72 also generates appropriate control signals which, whenapplied via leads 77 and 79, properly reset counters 76 and 74 for eachtiming interval. In addition, the control logic generates, on leads 34,appropriate select signals to the control input (C) of analog switch 35.These select signals cause the switch to route a particular one of itsinput voltages, namely the RTD voltage appearing on lead 195 or one oftwo reference voltages (v_(ref1) or v_(ref2) which are illustratively1.9 and zero volts, respectively) to an input of RTD input circuit 41for subsequent conversion by V/F converter 41 situated therein.Reference voltage v_(ref1) is supplied, via lead 38, from referencevoltage generator 39 which itself contains a well known highly stablevoltage source that exhibits negligible drift with temperaturevariations. As will be discussed hereinbelow and particularly withreference to RTD Temperature Processing Routine 1100 (discussed inconjunction with FIG. 11), the V/F converter is operated to perform aconversion every 0.1 seconds with each of eight analog voltages (ofwhich only those three that are relevant to the present invention beingspecifically shown and discussed herein) applied to the inputs (I₀, I₁and I₂ for the three voltages shown) of analog switch 35 being selected,on a time staggered basis, once every 0.8 seconds for conversion into acorresponding frequency value. Control logic 72 specifies which one ofthe input voltages to analog switch 35 is to be selected at any onetime. The states of circuit 70 are described in considerable detailbelow in conjunction with state table 400 and timing diagram 500 whichare respectively shown in FIGS. 4 and 5.

As circuit 70 cycles through its different states--of which there areeight in total, this circuit writes the value of its current state intoan internal register (not shown) which, when accessed by microcomputer80, applies this value onto leads 85. The microcomputer then reads thisvalue which, in turn, permits it to appropriately process the countedvalues provided by counters 75 and 78, via corresponding internalregisters (not shown) and leads 87 and 88. Leads 87 supply raw timingmeasurements, designated RAW₋₋ RATE₋₋ A and RAW₋₋ RATE₋₋ B, tomicrocomputer 80 for channel pairs A-C and B-C, respectively. Dependingupon the mode in which each channel pair is operating, RAW₋₋ RATE₋₋ Aand RAW₋₋ RATE₋₋ B will each provide, in terms of counts, a singleinter-channel phase difference measurement or a single Δt value for eachchannel pair. Leads 88 provide the microcomputer with the countedfrequency measurement data for the RTD and reference voltages. Inaddition, logic 72 also writes a value into another internal register(not specifically shown) which specifies which analog voltage is thenbeing selected by analog switch 35 for conversion by RTD input circuit42. This value is also read, via leads 85, by microcomputer 80.

Furthermore, the microcomputer applies appropriate signals onto leads 84to control the overall operation of circuit 70. The microcomputer alsoprovides appropriate address signals, via leads 82, to designate tocontrol logic 72 a specific internal register from which themicrocomputer is to read data or into which it will write data.

The microcomputer is also connected, via leads 91 and 93, torespectively well known output circuitry 90 which provides a number ofstandard outputs (such as illustratively a display interface(s),communication ports, 4-20 mA output lead 263 and scaled frequency outputlead 262) over leads 26, and to well known input circuitry 95 whichprovides the meter with interfaces to a number of well known inputdevices (such as switches, user keypads, communication ports and thelike).

Microcomputer 80 utilizes any one of many well known commerciallyavailable microprocessors (not specifically shown) along with sufficientrandom access memory (RAM) 83 for data storage and sufficient read onlymemory (ROM) 86 for program and constant storage. Inasmuch as thisprogram utilizes an event-driven task architecture, a database isimplemented within the microcomputer to facilitate easy transfer andsharing of measured and calculated data among the various tasks. Basedupon its input information, specifically the timing measurements,containing the inter-channel phase difference measurements and Δt valuesfor each pair of channels, and the counted frequency data along with thestate information--all of which are supplied by circuit 70,microcomputer 80 appropriately corrects the measured Δt values producedby each channel pair to account for the measured internal phase delaytherefor, determines an accurate temperature compensated meter factorand thereafter, using the corrected Δt values and this factor,determines the current mass flow and mass flow rate values--all of whichis discussed in greater detail below in conjunction with FlowMeasurement Basic Main Loop 600 shown in FIGS. 6A and 6B, ZeroDetermination Routine 700 shown in FIGS. 7A and 7B, Mechanical ZeroRoutine 800 shown in FIGS. 8A and 8B, and RTD Temperature ProcessingRoutine 1100 shown in FIG. 11.

To provide a thorough understanding of the interactions between circuit70 and microcomputer 80, this discussion will now address timing diagram400 and state table 500 shown in FIGS. 4A, 4B and 5 which collectivelydetail the functions provided by circuit 70 and their temporalrelationship. To facilitate understanding, the reader shouldsimultaneously refer to FIGS. 4A, 4B and 5 throughout the followingdiscussion.

Timing diagram 400 shown in FIGS. 4A and 4B defines the normalsequential modal operations for each of the channel pairs and thetemporal relationships therebetween.

As described above, each of the channel pairs, A-C and B-C, operates ineither a measurement mode or a zero mode. While one channel pairoperates in the measurement mode, the other operates in the zero modewith these operations reversing at the end of these modes. The durationof each of these modes (the "modal" interval) is always the same, i.e.time "t". In this regard, zero mode 410 for channel pair A-C andmeasurement mode 420 for channel pair B-C simultaneously operate, as domeasurement mode 440 and zero mode 450, zero mode 470 and measurementmode 480 for channel pairs A-C and B-C, respectively. Arrows 430, 460and 490 signify mode reversal between the channel pairs at theconclusion of three successive modal intervals.

Channel C is continuously supplied with the left (L) velocity sensorsignal and serves as the reference channel with respect to which theinternal phase delay of each of the other two channels is continuallymeasured. However, the input signals applied to non-reference channels Aand B are switched, depending upon the mode of corresponding channelpair A-C and B-C, between the left and right (R) velocity sensor signalswith phase difference measurements being taken for each different inputconfiguration to yield inter-channel phase difference measurements or Δtvalues for each pair.

In particular, while a channel pair operates in the measurement mode,the non-reference channel in that pair, e.g. channel A for pair A-C, issupplied with the right velocity sensor signal and measurements are madeof the inter-channel phase difference occurring for that pair. Thesemeasurements provide raw flow based Δt values. These measurements occurthroughout the entire time "t" that the channel exists in themeasurement mode. During this time, these measurements are provided tothe microcomputer for subsequent processing into corresponding mass flowrate values.

By contrast, four separate functions are performed in the followingsequence for any channel pair, e.g. pair B-C, during its zero mode: (a)switching the input for the non-reference channel in that pair from theright to the left velocity sensor signal during the switching interval,(b) providing measurements of the internal phase delay for that channelpair (i.e. "zeroing") during the zeroing interval, (c) switching thenon-reference channel input back to the right velocity sensor signalagain during a switching interval, and (d) permitting that pair to be"active" for a zeroing interval during which measurements of flow basedΔt values can be made. Since the opposite channel pair, e.g. pair A-C,will be actively measuring flow based Δt values during its measurementinterval while channel pair B-C is active, both channels are able toconcurrently provide flow based Δt values for the same velocity sensorsignals during this "active" interval. If additional error checking isneeded, the microcomputer can process the measurements provided by the"active" channel pair and compare the resulting corrected Δt valuesagainst those being provided using the other channel pair. A sufficientdiscrepancy therebetween would generally indicate an error condition.

As illustratively shown in FIGS. 4A and 4B, each switching interval is16 tube cycles in duration, while each zeroing interval occurs over 2048successive tube cycles. Accordingly, time "t" formed of two interleavedswitching and zeroing intervals occurs for 4128 tube cycles. Duringmeter initialization, microcomputer 80, shown in FIGS. 3A and 3B, loadsthe durations, in terms of tube cycles, of the switching and zeroingintervals into circuit 70 and specifically control logic 72 therein.

As shown in state table 500 depicted in FIG. 5 for circuit 70, thiscircuit, in normal operation, continuously cycles through eight statesin sequence, illustratively designated as states 26, 46, 26, 66, 6A, 6C,6A and 6E--of which two states, i.e. states 26 and 6A, are repeated.

Each of these states exists for a fixed duration, either the switchinginterval or the zeroing interval. During all eight states, the leftvelocity sensor signal is continuously applied to the input of referencechannel C.

For the first four states (states 26, 46, 26 and 66), channel pair A-Coperates in the measurement mode (hereinafter referred to as the channelA measurement mode) while channel pair B-C concurrently operates in itszero mode (hereinafter referred to as the Channel B zero mode).Throughout the channel A measurement mode, circuit 70 generates a lowlevel on multiplexor select signal RPO₋₋ A such that the right velocitysensor signal is continuously applied to the input of channel A. Duringthis mode, as indicated by the letter "X", channel pair A-C providesflow based Δt values and hence serves as the measuring channel pair. Inaddition, at the beginning of state 26, circuit 70 commences thebeginning of the channel B zero mode by initially applying a high levelto multiplexor select signal RPO₋₋ B in order to first switch thechannel B input from the right to the left velocity sensor signal. Thiscommences Channel B Switching state 26 during which channel pair B-Cundertakes no measurements but merely affords an adequate period oftime, i.e. switching interval t_(sw), for all switching transients andsimilar perturbations on channel B to settle out. Once this state iscompleted, circuit 70 invokes Channel Pair B-C Zeroing state 46. Duringstate 46, which lasts for zeroing interval t_(ZERO), inter-channel phasedifference measurements are continually made by circuit 70 for channelpair B-C. These measurements are read and averaged by the microprocessorto yield a measurement, in counts, of the internal phase delay for thatchannel pair. At the conclusion of the zeroing interval, Channel BSwitching state 26 re-occurs to switch the input of channel B from theleft velocity sensor signal back to the right velocity sensor signal. Todo so, circuit 70 generates a low level on multiplexor select signalRPO₋₋ B. Again, this state, during which no measurements are made onchannel pair B-C, remains in existence for the switching interval inorder to allow all switching transients and the like on channel B tosettle out. At the conclusion of state 26, Both Channels Active state 66occurs for a zeroing interval during which both channels are "active"and flow based Δt measurements can be made, if desired, through channelpair B-C in addition to those measurements simultaneously occurringthrough channel pair A-C. At the conclusion of state 66, states 6A, 6C,6A and 6E occur in sequence which merely provide the same operations buton the opposite channel pairs. All the states then repeat in seriatim,and so on.

B. SOFTWARE DESCRIPTION

With the above understanding in mind, the discussion will now addressvarious aspects of the software executed by microcomputer 80 shown inFIGS. 3A and 3B. Inasmuch as the microcomputer performs a number of wellknown administrative and control functions which are not relevant to thepresent invention--such as providing a database manager and anappropriate operating system environment for a task based applicationprogram, then, to simplify the following discussion, all of thesefunctions and the accompanying software therefor have been omittedherefrom.

FIG. 6 depicts a simplified flowchart of Flow Measurement Basic MainLoop 600. This routine provides the basic flow measurement functions.

Upon entry into routine 600, execution proceeds to block 610 which readscurrent raw phase difference measurement data (RAW₋₋ RATE₋₋ A and RAW₋₋RATE₋₋ B) and state information from circuit 70. Depending upon thecurrent mode of each channel pair, RAW₋₋ RATE₋₋ A and RAW₋₋ RATE₋₋ Bwill each provide, in counts, either a single interchannel phasedifference measurement or a single Δt value. After block 610 executes,block 620 is executed. This block executes Zero Determination Routine700 which, in response to the raw phase difference measurements andstate information and as discussed in detail below, processes the phasedifference data for the channel pair that is currently operating in themeasurement mode as a flow based Δt value and processes the phasedifference data for the other channel pair as an inter-channel phasedifference measurement. This measurement is used by this routine todetermine the electronic zero value for that latter channel pair. Theelectronic zero consists of two values, namely the internal phase delay,expressed in the same counts as Δt, associated with each of the twochannel pairs. Thereafter, routine 700 determines the mechanical zerofor the Coriolis meter. The mechanical zero is an offset value in the Δtmeasurements that is obtained, as described below, during a zero flowcondition occurring during meter calibration. After these operations arecompleted, routine 700 then corrects the current Δt value measured forthe channel pair operating in the measurement mode by the mechanicalzero for the meter and by the most current electronic zero value forthat pair--this electronic zero value having been previously determinedwhile that pair was last operating in its zero mode.

After routine 700 has fully executed, execution proceeds from block 620to 630. The latter block, when executed, filters the corrected Δt valueproduced by block 620 through a double pole software filter to removenoise and the like thereby yielding a current filtered Δt value.Execution next proceeds to block 640 which calculates the currentvolumetric and mass flow rates using the current filtered Δt value andthe temperature corrected rate factor. This temperature factor isupdated on a periodic basis through RTD Temperature Processing Routine1100 which, as described in detail below, executes on an interruptbasis.

Upon completion of block 640, block 650 is executed. This latter blocktests the volumetric and mass flow rate values against corresponding lowflow (cutoff) limit conditions and, if these conditions are met,temporarily sets the volumetric and mass flow rates to zero. Thereafter,execution proceeds to block 660 which, when executed, stores the currentvolumetric and mass flow values in the database for subsequent use, suchas for periodic updating of the displays, totalized flow readings and/ormeter outputs. Execution then loops back to routine 610 and so on.

A flowchart of Zero Determination Routine 700 is collectively depictedin FIGS. 7A and 7B for which the correct alignment of the drawing sheetsis shown in FIG. 7. This routine contains four separate sections:Electronic Zero Determination Routine 710, Electronic Zero CompensationRoutine 760, Mechanical Zero Determination Routine 780, and MechanicalZero Compensation Routine 790. As generally discussed above, routine700, specifically through routine 710, determines the current flow basedΔt value for the channel pair currently operating in the measurementmode and determines the current electronic zero value for the otherchannel pair operating in its zero mode. Routine 760 compensates eachcurrent measured Δt value from the channel pair operating in themeasurement mode by the most recent electronic zero value for thatchannel. Routine 780 determines the mechanical zero for the meter.Finally, routine 790 corrects the flow based Δt value for the currentchannel pair operating in its measurement mode by the mechanical zerovalue for the meter.

Specifically, upon entry into routine 700 and specifically into routine710, execution first proceeds to decision block 703. This blockdetermines whether the value of variable STATE indicates that channelpair A-C is zeroing, i.e. the state of circuit 70 is given by the value"6C" (see FIG. 5). This value is provided by circuit 70 upon inquiry bymicroprocessor 80 (see FIGS. 3A and 3B). In the event that this state isnow occurring, then execution proceeds, via the YES path emanating fromdecision block 703 as shown in FIGS. 7A and 7B, to block 706. Thislatter block, when executed, updates the value of a totalized ratevariable (TOTAL₋₋ RATE) with the current value of RAW₋₋ RATE₋₋ A. Aswill be seen at the conclusion of the zeroing interval, this totalizedrate value is set equal to zero. Next, block 709 is executed to set thestate of a temporary flag (TEMP₋₋ STATE) to a value (ZEROING₋₋ CHANNEL₋₋A) that signifies that channel pair A-C is presently undergoing zeroing.Once this occurs, execution proceeds to block 712 to merely incrementthe value of a loop counter (COUNTER) by one. Execution then proceeds todecision block 730. Alternatively, in the event that the current valueof variable STATE indicates that channel pair A-C is not zeroing, thenexecution proceeds, via the NO path emanating from decision block 703,to decision block 715. The latter decision block tests the state of thetemporary flag to determine if zeroing has just terminated for channelpair A-C, i.e. whether the value of this flag still equals ZEROING₋₋CHANNEL₋₋ A. In the event that zeroing has just terminated for thischannel pair, then decision block 715 routes execution, via its YESpath, to block 718. This latter block, when executed, calculates theelectronic zero value for channel pair A-C, i.e. ELECT₋₋ ZERO₋₋ A, as asimple average value of the separate measurements that have beentotalized, specifically the value of the variable TOTAL₋₋ RATE dividedby the contents of loop counter COUNTER. Once this has occurred,execution proceeds to block 721 which sets the value of the temporaryflag to another value, here NOT₋₋ ZEROING₋₋ CHANNEL₋₋ A, that signifiesthat channel pair A-C is not undergoing zeroing. Thereafter, executionproceeds to block 724 which merely resets the values of both the loopcounter and the totalized rate variable to zero. Execution then proceedsto decision block 730. Alternatively, execution also proceeds to thisdecision block, via the NO path emanating from decision block 715, inthe event that channel pair A-C has not been and has not just completedzeroing.

Blocks 730 through 751 provide the same operations as do blocks 703-724but for determining the value of the electronic zero for channel pairB-C, i.e. ELECT₋₋ ZERO₋₋ B. Specifically, decision block 730 determineswhether the value of variable STATE indicates that channel pair B-C iszeroing, i.e. the state of circuit 70 is given by the value "46" (seeFIG. 5). In the event that this state is now occurring, then executionproceeds, via the YES path emanating from decision block 730 as shown inFIGS. 7A and 7B, to block 733. This latter block, when executed, updatesthe value of the totalized rate variable, TOTAL₋₋ RATE, with the currentvalue of RAW₋₋ RATE₋₋ B. As will be seen at the conclusion of thiszeroing interval, this totalized rate value is set equal to zero. Next,block 736 is executed to set the state of the temporary flag, TEMP₋₋STATE, to a value (ZEROING₋₋ CHANNEL₋₋ B) that signifies that channelpair B-C is presently undergoing zeroing. Once this occurs, executionproceeds to block 739 to merely increment the value of the loop counter,COUNTER, by one. Execution then proceeds to routine 760. Alternatively,in the event that the current value of variable STATE indicates thatchannel pair B-C is not zeroing, then execution proceeds, via the NOpath emanating from decision block 730, to decision block 742. Thelatter decision block tests the state of the temporary flag to determineif zeroing has just terminated for channel pair B-C, i.e. whether thevalue of this flag still equals ZEROING₋₋ CHANNEL₋₋ B. In the event thatzeroing has just terminated for this channel pair, then decision block742 routes execution, via its YES path, to block 745. This latter block,when executed, calculates the electronic zero value for channel pairB-C, i.e. ELECT₋₋ ZERO₋₋ B, as a simple average value of the separatemeasurements that have been totalized, specifically the value of thevariable TOTAL₋₋ RATE divided by the contents of loop counter COUNTER.Once this has occurred, execution proceeds to block 748 which sets thevalue of the temporary flag to another value, here NOT₋₋ ZEROING₋₋CHANNEL₋₋ B, that signifies that channel pair B-C is not undergoingzeroing. Thereafter, execution proceeds to block 751 which merely resetsthe values of both the loop counter and the totalized rate variable tozero. Execution then proceeds to routine 760. Alternatively, executionalso proceeds to this routine in the event that channel pair B-C has notbeen and has not just completed zeroing, i.e. via the NO path emanatingfrom decision block 742. At this point, routine 710 has completedexecution. Inasmuch as one of the channel pairs is operating in its zeromode at any one time, then the current value of the correspondingvariable ELECT₋₋ ZERO₋₋ A or ELECT₋₋ ZERO₋₋ B is being determined atthat time with the appropriate steps, as described above, being executedtherefor.

Electronic Zero Compensation Routine 760 merely corrects (compensates)the current Δt measurement by the electronic zero value for theparticular channel pair that produced that measurement. Specifically,upon entry into this routine, execution proceeds to decision block 763which, based upon whether channel pair B-C or channel pair A-C iscurrently operating in its measurement mode, respectively routesexecution to block 767 or 769. In the event that execution is routed toblock 767, then, this block, when executed, subtracts the electroniczero value for channel pair B-C from RAW₋₋ RATE₋₋ B and stores theresult in variable Δt. Alternately, if execution is routed to block 769,then, this block, when executed subtracts the electronic zero value forchannel pair ADC from RAW₋₋ RATE₋₋ A and stores the result in variableΔt. After either block 767 or 769 has executed, execution proceeds toMechanical Zero Determination Routine 780.

Routine 780 determines the current value mechanical zero value for themeter. Specifically, upon entering routine 780, execution proceeds todecision block 781. This block, when executed, determines if a currentmechanical zero value is to be found. As noted above, a mechanical zerois determined under no flow conditions during meter calibration. Ifmeter calibration is currently being performed and if a user indicatesthat no flow is occurring by depressing an appropriate pushbutton on themeter electronics, then decision block 781 routes execution, via its YESpath, to block 784. This latter block executes Mechanical Zero Routine800, as discussed in detail below, to determine the current mechanicalzero value (MECH₋₋ ZERO) for the meter. Once this value has beendetermined, execution proceeds to Mechanical Zero Compensation Routine790. Execution also proceeds to routine 790, via the NO path emanatingfrom decision block 781, in the event that meter calibration is notoccurring or if it is that the user has not specified that no flow isoccurring.

Mechanical Zero Routine 790 contains block 792, which, when executed,merely subtracts the current mechanical zero value, MECH₋₋ ZERO, fromthe value of variable Δt with the result being a corrected Δtmeasurement which will be subsequently filtered and used by main loop600 (specifically blocks 630 and 640 therein as shown in FIGS. 6A and6B) to determine the current value for mass flow rate. Once block 792has executed, execution exits from routines 790 and 700, as shown inFIGS. 7A and 7B, and returns to Flow Measurement Basic Main Loop 600.

To simplify the software, routine 700 does not include appropriatesoftware for determining corresponding corrected Δt values for bothchannel pairs during each "active" interval and, as discussed above,comparing the results to detect sufficient discrepancies therebetweenand system errors associated therewith. Routine 700 can be readilymodified by any one skilled in the art to include this software.

FIGS. 8A and 8B collectively depict a flowchart of Mechanical ZeroRoutine 800; the correct alignment of the drawing sheets for thisfigures is shown in FIG. 8. As discussed above, routine 800 determinesthe current value for the mechanical zero of the meter. In essence andas discussed above, the current value of this zero is determined byfirst calculating the standard deviation, σ.sub.Δt, of the Δt valuesobtained for a no flow condition during meter calibration. This standarddeviation provides a measure of the noise appearing on the Δtmeasurements at a no flow condition. Only if the noise is sufficientlylow, i.e. the value of the standard deviation is below a minimumthreshold value, will the most recent value for the mechanical zero beupdated to reflect its current value; otherwise, this current value willsimply be ignored. The number of measured Δt values used in determiningthe standard deviation is governed by any one of three criteria: (a)when the "running" standard deviation decreases below a convergencelimit, (b) a user terminates the mechanical zeroing by depressing anappropriate pushbutton, or (c) if a pre-defined number of measured Δtvalues has been taken. In addition, appropriate limits checks are madeto ensure that the current value of the mechanical zero lies withinpre-defined bounds prior to replacing its most recent value with itscurrent value.

Specifically, upon entry into routine 800, execution proceeds todecision block 803. This block, when executed, tests the status of aflag (ZERO STATE) to specify whether the process of determining amechanical zero is currently occurring. This flag is set by appropriatesoftware (not shown) to commence this process. In the event that thisprocess is underway, decision block 803 routes execution, via its YESpath, to block 806. This latter block, when executed, updates the valueof a totalized variable (ZERO₋₋ TOTAL) with the current Δt value. Aswill be seen later, this totalized value is set equal to zero at theconclusion of the zeroing interval. Once block 806 has executed,execution proceeds to block 809 to increment the contents of a loopcounter, ZERO₋₋ COUNT, by one. Thereafter, execution proceeds todecision block 820. Alternatively, if a mechanical zero value is notcurrently being determined, i.e the status of the ZERO STATE flag is nownot active, then execution proceeds, via the NO path emanating fromdecision block 803, to block 812. This latter block resets the ZERO₋₋STATE flag to the active state, sets the values of oth the ZERO₋₋ TOTALand loop counter ZERO₋₋ COUNT to zero, and set the value of variable,MIN₋₋ STD₋₋ DEV, to a large predefined number (the exact value of whichis not critical as long as it is well in excess of the expected value ofthe standard deviation). Thereafter, block 816 is executed to reset allthe error flags that are associated with the mechanical zero process.After this occurs, execution proceeds to decision block 820.

Decision block 820, when executed, determines whether a minimum numberof measured Δt values has occurred to determine a mechanical zerovalue--i.e. specifically whether the current value of loop counterZERO₋₋ COUNT exceeds a predefined minimum value, MIN₋₋ ZERO₋₋ COUNTwhich typically equals the decimal value "100". In the event that aninsufficient number of Δt values has occurred, then execution exits fromroutine 800, via path 872 and NO path 822 emanating from decision block820. Alternatively, if a minimum number of Δt values has occurred, thendecision block 820 routes execution, via its YES path, to block 823.This latter block, when executed, updates the standard deviation, σ, ofthe Δt values that have been currently measured thusfar for use indetermining a mechanical zero value and stores the result in variableSTD₋₋ DEV. Once this occurs, execution proceeds to decision block 826which tests the resulting standard deviation value against a minimumvalue therefor. In the event that the resulting standard deviation isless then the minimum value, decision block 826 routes execution, viaits YES path, to block 829. This latter block calculates a temporarycurrent value for the mechanical zero (MECH₋₋ ZERO₋₋ TEMP) as being anaverage of the totalized Δt values obtained thusfar during the currentmechanical zero process, i.e. the value of ZERO₋₋ TOTAL divided by thecontents of loop counter ZERO₋₋ COUNT. Once this occurs, block 829 setsa minimum standard deviation value equal to the current value of thestandard deviation. By doing so, the minimum value of the standarddeviation that has been determined thusfar for this current mechanicalzero process will always be used, in the manner discussed below, todetermine whether the current value of the mechanical zero is too noisyand hence unacceptable. Once block 829 fully executes, executionproceeds to decision block 832. Alternatively, execution also proceedsto this decision block, via the NO path emanating from decision block826, in the event that the current value of the standard deviation nowequals or exceeds its minimum value.

At this point, up to three separate tests are undertaken in seriatimthrough decision blocks 832, 836 and 840 to determine if a sufficientnumber of measured Δt values has been taken to determine the currentmechanical zero value. Such measurements continue until a sufficientnumber has occurred. In particular, decision block 832 determineswhether the current value of the standard deviation is less than aconvergence limit. In this case, if the standard deviation has beenfalling with successive Δt values and has fallen below a predefinedlimit value, then it is very unlikely that any additional measurementswill adversely impact the mechanical zero value. Accordingly, if thestandard deviation has decreased in this manner, than decision block 832routes execution, via its YES path, to decision block 843.Alternatively, if the current value of the standard deviation is stillhigher than the convergence limit, then execution proceeds, via the NOpath emanating from decision block 832, to decision block 836. Thislatter decision block determines whether the user has depressed apushbutton or otherwise provided an appropriate indication to the meterto terminate the current mechanical zero process. In the event that theuser terminated this process, then decision block 836 routes execution,via its YES path, to decision block 843. Alternatively, if the user hasnot terminated the current mechanical zero process, then decision block836 routes execution, via its NO path, to decision block 840. Decisionblock 840, when executed, determines whether a maximum number, MAX₋₋COUNT, of the measured Δt values has just occurred. In the event thatthis maximum number of measurements, e.g. 2000 measurements, hasoccurred, then decision block 840 routes execution, via its YES path, todecision block 843. Alternatively, if the maximum number of suchmeasurements has not occurred, then execution exits from routine 800,via NO path 841 emanating from decision block 840 and via path 872, inorder to appropriately process the next successive Δt measurement.

At this point in routine 800, a current value, though temporary, for themechanical zero has been determined based upon a sufficient number ofsuccessive Δt measurements. Decision blocks 843, 846 and 849 nowdetermine whether this mechanical zero value lies within predefinedlimits, e.g. illustratively ±3 μsec, and whether this mechanical zerovalue is relatively noise-free. Specifically, decision block 843determines whether the current temporary mechanical zero value is lessthan a lower limit, i.e. illustratively -3 μsec. In the event that thislimit is negatively exceeded, then decision block 843 routes execution,via its YES path, to block 854. Since this signifies an error condition,block 854, when executed, sets the value of an appropriate error flag,i.e. MECHANICAL ZERO TOO LOW, to true. Alternatively, if the lower limitis not negatively exceeded, then decision block 843 routes execution,via its NO path, to decision block 846. This latter decision blockdetermines whether the current temporary mechanical zero value isgreater than an upper limit, i.e. illustratively +3 μsec. In the eventthat this limit is positively exceeded, then decision block 846 routesexecution, via its NO path, to block 859. Since this signifies an errorcondition, block 859, when executed, sets the value of an appropriateerror flag, i.e. MECHANICAL ZERO TOO HIGH, to true. The upper and lower±3 μsec limit values were determined empirically as being those valueswithin which all no-flow based Δt values should lie for meters that arecurrently manufactured by the present assignee. Alternatively, ifneither of these limits is exceeded, then decision block 846 routesexecution, via its NO path, to decision block 851. This latter decisionblock determines whether the temporary mechanical zero value issufficiently noise-free, i.e. whether all the successive Δt values thatare utilized to generate this value possess less than a givenvariability, by comparing the present minimum standard deviation valueagainst a limit equal to a preset integer multiple ("n") of, typicallytwice, the convergence limit.

In this regard, the most repeatable value for the mechanical zero tendsto occur when the standard deviation reaches its minimum value. Itappears that this occurs because the measured Δt values will becorrupted by periodic noise, such as 60 Hz hum and its harmonics, thatbeats against the sampling rate of the velocity sensor signals (i.e.counters 75 are read once every tube cycle) thereby creating beatfrequencies that appear in the measured Δt values. In normal operation,I expect that some noise of this type will always be present, though theamplitude of the noise will usually vary from one installation toanother. For the range of meters manufactured by the present assignee,the velocity signals have fundamental frequencies in the range of 30-180Hz. The amplitude of the beat frequencies will be lowest when the noiseis in-phase with this sampling rate and will increase as the noise getsprogressively out-of-phase with the sampling rate thereby leading toincreased variability and error in the measured no flow Δt values.Hence, the minimum value of the standard deviation is used to determinewhether the resulting mechanical value will be too noisy. Specifically,if decision block 851 determines that the minimum standard deviationexceeds the limit of "n" times the convergence limit, then the currenttemporary mechanical zero value is simply too noisy and is ignored.Since this signifies an error condition, decision block 851 routesexecution, via its YES path, to block 862. This latter block, whenexecuted, sets the value of an appropriate error flag, i.e. MECHANICALZERO TOO NOISY, to true. Alternatively, if the minimum standarddeviation is sufficiently low, hence indicating that the temporarymechanical zero value, is relatively noise-free, then decision block 851routes execution, via its NO path, to block 865. This latter blockupdates the mechanical zero value, MECH₋₋ ZERO, as being equal to thevalue of the temporary mechanical zero, MECH₋₋ ZERO₋₋ TEMP. Once block854, 859, 862 or 865 has executed, execution proceeds to block 870which, in turn, sets the state of flag ZERO₋₋ STATE to inactive toreflect that the mechanical zero process has been terminated and is nownot in progress. Once this occurs, execution then exits from routine800.

Having described the mechanical zero process, FIG. 9 diagrammaticallyshows the associated zeroing operations that occur for eachcorresponding range in the standard deviation, σ.sub.Δt, that can beobtained during this process. Specifically, whenever the value ofσ.sub.Δt lies within region 910 and hence is less than the convergencelimit (1), zeroing immediately stops and the resulting mechanical zerovalue is accepted. For any value of σ.sub.Δt lying within region 920 andhence greater than the convergence limit but less than "n" times thatlimit, zeroing continues until a maximum number, as given by the valueof variable MAX₋₋ COUNT, of Δt measurements has occurred. This number,in tube cycles, defines a maximum zeroing interval. For any value ofσ.sub.Δt that lies within region 930 and hence exceeds "n" times theconvergence limit, zeroing immediately halts. The associated currentmechanical zero value is simply ignored in favor of its most recentvalue.

FIG. 10 diagrammatically shows the ranges of acceptable andnon-acceptable mechanical zero values. As shown, erroneous mechanicalzero values are those which lie either within region 1020 and hence arenegatively greater than the negative limit of -3 μsec or those which liewithin region 1030 and are positively greater than the positive limit of+3 μsec. If the mechanical zero is determined as having any of thesevalues, that value is simply ignored. Only those values for themechanical zero that lie within region 1010 and hence are situatedbetween the negative and positive limits are accepted.

FIG. 11 shows a flowchart of RTD Temperature Processing Routine 1100. Asdiscussed above, this routine operates on a periodic interrupt basis,every 0.8 seconds, to provide a digitized flow tube temperature valuethat is essentially insensitive to temperature drift of the RTD and,using that value, calculates a current value for the temperaturecompensated meter factor (RF). This value is then stored in the databasewithin the microcomputer for subsequent use by routine 600 indetermining a current mass flow rate value.

Upon entry into routine 1100, execution proceeds to block 1110. Thisblock, when executed, causes analog switch 35 to route the RTD voltageto the input of V/F converter 41 (see FIGS. 3A and 3B) for subsequentconversion. To specifically effectuate this, microprocessor 80 appliessuitable address and control signals, via leads 82 and 84, to circuit 70and particularly to control logic 72 situated therein. These signals, inturn, instruct that logic to apply the appropriate select signals overleads 34 to the analog switch. After this occurs and an appropriatecounting interval has elapsed, block 1110, shown in FIG. 11, reads thecontents of counter 78, shown in FIGS. 3A and 3B, which contains acounted value proportional to the frequency converted analog RTDvoltage. Thereafter, as shown in FIG. 11, execution proceeds to block1120. This block, when executed, filters the contents that have beenread from counter 78 through a two-pole software filter and stores theresulting filtered value in temporary variable V₋₋ TO₋₋ F.

After this occurs, block 1130 is executed which eliminates a zero offsetvalue from the filtered value to yield a current frequency value,CURRENT₋₋ FREQ. This zero offset value, FREQ₋₋ AT₋₋ 0 V, is a non-zerofiltered counted frequency output value produced by the V/F converterwith a zero input voltage (v_(ref1)) applied thereto. Thereafter, block1140 is executed to calculate a proportionality factor, FREQ₋₋ PER₋₋ C,that specifies the number of counts per degree C. This factor is simplygiven by the difference in the filtered counted values for two referencevoltages (v_(ref1) and v_(ref2) which are illustratively groundpotential and 1.9 V, respectively) divided by the decimal number "380".Since the counted frequency values for both reference voltages areobtained essentially contemporaneously with any change in the flow tubetemperature, then any temperature drift produced by the V/F converterwill inject an essentially equal error component into both of thesecounted values. Inasmuch as the proportionality factor is calculatedusing the difference between these counted values rather than themagnitude of either value alone, the value of the proportionality factorwill be essentially unaffected by any shift in the counted V/F outputattributable to temperature drift. The zero offset value (FREQ₋₋ AT₋₋ OV) and the filtered counted 1.9 V reference value (FREQ₋₋ AT₋₋ 1.9 V)are both determined on a periodic interrupt basis, again every 0.8seconds, by another routine not shown. This routine, which would bereadily apparent to anyone skilled in the art, causes circuit 70 toapply appropriate select signals to the analog switch to first route ona time staggered basis either the ground potential (v_(ref1)) or 1.9 V(v_(ref2)) to the input of V/F converter 41, and then sequentially countthe frequency value produced therefrom and thereafter read and filterthis value and store the filtered results.

Once the proportionality factor has been determined by block 1140,execution proceeds to block 1150. This block calculates the currenttemperature (TEMP) sensed by the RTD by dividing the current frequencyvalue by the proportionality factor. Thereafter, execution proceeds toblock 1160 which calculates the temperature compensated meter factor RFusing a meter factor value and the current temperature value. For aCoriolis meter, its meter factor is a known constant that is determinedempirically during manufacture. Once this temperature compensated meterfactor is calculated, it is stored in the database for subsequent use indetermining mass flow rate. Execution then exits from routine 1100.

Those skilled in the art will now certainly realize that although bothchannel pairs are operated in parallel, such that one pair is operatingin its zero mode while the other pair is operating in its measurementmode, these channel pairs could be sequentially operated. In thisinstance, an operating channel pair would function in its zero and/ormeasurement modes while the other channel pair remained in a standbystatus. The channel pairs could then periodically switch from operatingto standby status at the conclusion of each mode or after the operatingchannel pair sequentially undertook both its zero and measurement modes.Since, with sequential operation, one channel pair is always in thestandby status at any one time, then, to simplify the circuitry, onechannel pair rather than two could be used with that one pair alwaysoperating and continuously cycling between its measurement and zeromodes. In those instances when the one effectively operating channelpair is undertaking its zero mode, no flow measurements would then bebeing made. Accordingly, an assumption, in lieu of actual flowmeasurements, would need to be made regarding the flow that is occurringduring that time. Hence, by eliminating continuous flow measurements,the use of effectively only one operating channel pair at any one timein a Coriolis flow meter--regardless of whether the meter contains onlyone physical channel pair that is cycled between its two modes or twopairs with one such pair being inactive at any one time, may provideflow measurements that are somewhat inaccurate. By contrast, since myinventive flow measurement circuit 30 always has one channel pair that,during normal flow metering operations, is actively measuring actualflow at any time, the member provides very accurate flow measurements atthe expense of a slight increase in circuit complexity.

Furthermore, although an "active" interval has been provided within thezero mode for any channel pair during which, for example, dual flowmeasurements and inter-channel pair comparisons thereof could be made,this interval could be eliminated, if needed, with no adverse affect onmeter accuracy. In fact, doing so could either be used to shorten theduration of the zero mode by one zeroing interval (i.e. the time duringwhich the channel pair would otherwise operate in the "active" interval)or lengthen the time during which that channel pair is actually zeroingby appropriately increasing the number of internal phase delaymeasurements that are to be taken then.

Also, those skilled in the art recognize that, although the disclosedembodiment utilizes U-shaped flow conduits, flow conduits (tubes) ofalmost any size and shape may be used as long as the conduits can beoscillated about an axis to establish a non-inertial frame of reference.For example, these conduits may include but are not limited to straighttubes, S-shaped conduits or looped conduits. Moreover, although themeter has been shown as containing two parallel flow tubes, embodimentshaving a single flow tube or more than two parallel flow tubes--such asthree, four or even more--may be used if desired.

Although a single embodiment of the invention has been shown anddescribed in detail herein, many other varied embodiments that stillincorporate the teachings of the present invention can be readilyfabricated by those skilled in the art.

I claim:
 1. Circuitry for measuring first and second input signalscomprising:first, second and third input channels, having first, secondand third channel inputs, for respectively producing first, second andthird channel output signals in response to a predeterminedcharacteristic of said first, second and third channel inputs;measurement means comprising:means, responsive to said first, second andthird channel output signals for determining first and second internaloffset values respectively associated with first and second pairs ofsaid input channels and for respectively measuring first and secondsignal values through said first and second pairs so as to produce firstand second measured signal values; and means, responsive to said firstand second measured signal values and said first and second internaloffset values, for respectively compensating said first and secondmeasured signal values by said first and second internal offset valuesto yield first and second compensated values, respectively, asmeasurements of said first and second input signals; means forselectively routing said first or second input signals to correspondinginputs of said first, second and third input channels; and controlmeans, connected to said selectively routing means and to saidmeasurement means, for specifying which one of said input signals is tobe simultaneously applied as input to each one of the input channels andfor operating said selectively routing means and said first and secondpairs of the input channels in conjunction with said measurement meanssuch that while the first pair is determining the first internal offsetdelay value the second pair is measuring the second signal value and forreversing operation of said channel pairs after a pre-defined intervalof time has elapsed such that the first pair will measure the signalvalue while the second pair will determine the second internal offsetdelay value so as to continuously measure the first and second inputsignals and compensate measurements of the first and second inputsignals produced by each of the channel pairs by the value of theinternal offset associated with that particular channel pair.
 2. Thecircuitry in claim 1 further comprising:input multiplexor means,connected to the first and second input signals, for providing first,second and third multiplexor outputs and, operative in response toselect signals, for selectively routing said first or second inputsignals to each of said first, second or third multiplexor outputs; saidfirst, second and third channel inputs being respectively connected tothe first, second and third multiplexor outputs; first and secondmeasuring means connected to the first and second channel outputsignals, and to said second and third channel output signals,respectively, so as to define the first and second channel pairs,wherein said first and second channel pairs respectively measure thepre-determined characteristic of the first and second channel pairoutput signals and said second and third channel pair output signals;and said control means comprises:logic means, connected to said firstand second measuring means and to said input multiplexor means, forgenerating said select signals so as to continuously route said first orsecond input signal to the second multiplexor output and to selectivelyroute either said first or second signal to each of said first and thirdmultiplexor outputs so as to operate said first and second channel pairssuch that both of said channel pairs simultaneously operate in differingones of first or second modes and each of said channel pairsrepetitively cycles between the first and second modes; wherein:for oneof said channel pairs operating in said first mode the first or secondinput signal is applied to both the channel inputs of said one channelpair such that a first measured value produced thereby reflects a valueof the pre-defined offset internally produced by said one channel pair;and for an opposite one of said channel pairs operating in said secondmode, the first and second input signals are applied to correspondingones of said channel inputs of said opposite channel pair such that asecond measured value produced thereby reflects a desired characteristicof said first and second input signals.
 3. The circuitry in claim 2wherein, for either one of said first or second channel pairs, the firstmode comprises, in succession, a first switching interval during whichone of the channel inputs to the one channel pair is switched throughsaid input multiplexor means from the second input signal to the firstinput signal, a zeroing interval during which the one channel pairgenerates a plurality of first measured values, and a second switchinginterval during which the one channel input is switched through theinput multiplexor means back from said first input signal to said secondinput signal.
 4. The circuitry in claim 3 wherein the first and secondswitching intervals are equal in duration to each other and are eachsufficiently long enough such that switching transients occurring duringeach of these intervals decrease to a pre-defined level.
 5. Thecircuitry in claim 4 wherein said logic means further comprises:meansfor generating said select signals and for providing state informationsignifying a current state of each one of said channel pairs; andprocessor means, operative in response to said first and second measuredvalues produced by each of the channel pairs and to said stateinformation, for compensating each of a plurality of second measuredvalues produced by said one channel pair operating in the second mode bythe first measured value previously obtained for that channel pairduring its operation in the first mode.
 6. The circuitry in claim 5wherein said desired characteristic is a time difference (at) occurringbetween corresponding points on said first and second input signals, andsaid first measured value for the first and second channel pairsrespectively reflect internal phase delay for said first and secondchannel pairs.
 7. The circuitry in claim 6 wherein said first and secondmeasurement means each comprises a counter.
 8. The circuitry in claim 7wherein said predetermined characteristic for said signals applied tosaid first, second or third channel inputs is given by a time when asignal applied to said first, second or third channel inputsrespectively equals a pre-defined amplitude.
 9. In circuitry formeasuring first and second input signals, a method comprising the stepsof:respectively producing through first, second and third input channelshaving first, second and third channel inputs first, second and thirdchannel output signals in response to a predetermined characteristic ofsaid first, second and third channel inputs; determining, in response tosaid first, second and third channel output signals, first and secondinternal offset values respectively associated with first and secondpairs of said input channels and respectively measuring first and secondsignal values through said first and second pairs so as to produce firstand second measured signal values; respectively compensating, inresponse to said first and second measured signal values and said firstand second internal offset values, the first and second measured signalvalues by said first and second internal offset values to yield firstand second compensated values, respectively, as measurements of saidfirst and second input signals; selectively routing said first or secondinput signals to corresponding inputs of said first, second and thirdinput channels; and specifying, to said selectively routing step, whichone of said input signals is to be simultaneously applied as input toeach one of the input channels, operating said selectively routing meansand said first and second pairs of the input channels in conjunctionwith said measurement means such that while the first pair isdetermining the first internal offset delay value the second pair ismeasuring the second signal value and reversing operation of saidchannel pairs after a pre-defined interval of time has elapsed such thatthe first pair will measure the signal value while the second pair willdetermine the second internal offset delay value so as to continuouslymeasure the first and second input signals and compensate measurementsof the first and second input signals produced by each of the channelpairs by the value of the internal offset associated with thatparticular channel pair.
 10. The method in claim 9 further comprisingthe steps of:providing through input multiplexor means, connected to thefirst and second input signals, first, second and third multiplexoroutputs and, operative in response to select signals, for selectivelyrouting said first or second input signals to each of said first, secondor third multiplexor outputs; said first, second and third channelinputs being respectively connected to the first, second and thirdmultiplexor outputs; first and second measuring means connected to thefirst and second channel output signals, and to said second and thirdchannel output signals, respectively, so as to define the first andsecond channel pairs, wherein in said first and second channel pairsrespectively measuring the pre-determined characteristic of the firstand second channel pair output signals and said second and third channelpair output signals; and generating said select signals so as tocontinuously route said first or second input signal to the secondmultiplexor output and to selectively route either said first or secondsignal to each of said first and third multiplexor outputs so as tooperate said first and second channel pairs such that both of saidchannel pairs simultaneously operate in differing ones of first orsecond modes and each of said channel pairs repetitively cycles betweenthe first and second modes; wherein:for one of said channel pairsoperating in said first mode applying the first or second input signalto both the channel inputs of said one channel pair such that a firstmeasured value produced thereby reflects a value of the pre-definedoffset internally produced by said one channel pair; and for an oppositeone of said channel pairs operating in said second mode applying thefirst and second input signals to corresponding ones of said channelinputs of said opposite channel pair such that a second measured valueproduced thereby reflects a desired characteristic of said first andsecond input signals.
 11. The method in claim 10 wherein, for either oneof said first or second channel pairs, the first mode comprises, insuccession, a first switching interval during which one of the channelinputs to the one channel pair is switched through said inputmultiplexor means from the second input signal to the first inputsignal, a zeroing interval during which the one channel pair generates aplurality of first measured values, and a second switching intervalduring which the one channel input is switched through the inputmultiplexor means back from said first input signal to said second inputsignal.
 12. The method in claim 11 wherein the first and secondswitching intervals are equal in duration to each other and are eachsufficiently long enough such that switching transients occurring duringeach of these intervals decrease to a pre-defined level.
 13. The methodin claim 12 further comprising the steps of:generating said selectsignals and for providing state information signifying a current stateof each one of said channel pairs; and compensating, in response to saidfirst and second measured values produced by each of the channel pairsand to said state information, each of a plurality of second measuredvalues produced by said one channel pair operating in the second mode bythe first measured value previously obtained for that channel pairduring its operation in the first mode.
 14. The method in claim 13wherein said desired characteristic is a time difference (Δt) occurringbetween corresponding points on said first and second input signals, andsaid first measured value for the first and second channel pairsrespectively reflect internal phase delay for said first and secondchannel pairs.
 15. The method in claim 14 wherein said predeterminedcharacteristic for said signals applied to said first, second or thirdchannel inputs is given by a time when a signal applied to said first,second or third channel inputs respectively equals a pre-definedamplitude.